5962-8964401PA(2001) Просмотр технического описания (PDF) - Analog Devices

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5962-8964401PA
(Rev.:2001)

60 MHz, 2000 V/μs Monolithic Op Amp

Analog Devices 

AD844

Input Impedance

At low frequencies, negative feedback keeps the resistance at the

inverting input close to zero. As the frequency increases, the

impedance looking into this input will increase from near zero to

the open loop input resistance, due to bandwidth limitations,

making the input seem inductive. If it is desired to keep the

input impedance flatter, a series RC network can be inserted

across the input. The resistor is chosen so that the parallel sum

of it and R2 equals the desired termination resistance. The

capacitance is set so that the pole determined by this RC network

is about half the bandwidth of the op amp. This network is not

important if the input resistor is much larger than the termina-

tion used, or if frequencies are relatively low. In some cases, the

small peaking that occurs without the network can be of use in

extending the –3 dB bandwidth.

Driving Large Capacitive Loads

Capacitive drive capability is 100 pF without an external net-

work. With the addition of the network shown in Figure 7, the

capacitive drive can be extended to over 10,000 pF, limited by

internal power dissipation. With capacitive loads, the output

speed becomes a function of the overdriven output current

limit. Since this is roughly ± 100 mA, under these conditions,

the maximum slew rate into a 1000 pF load is ± 100 V/µs.

Figure 8 shows the transient response of an inverting amplifier

(R1 = R2 = 1 kΩ) using the feed forward network shown in

Figure 7, driving a load of 1000 pF.

AD844

VOUT

CL

750⍀

22pF

Figure 7. Feed Forward Network for Large Capacitive

Loads

Schottky diodes, to create the error signal and limit the input

signal to the oscilloscope. For measuring settling time, the ratio

of R6/R5 is equal to R1/R2. For unity gain, R6 = R5 = 1 kΩ,

and RL = 500 Ω. For the gain of –10, R5 = 50 Ω, R6 = 500 Ω

and RL was not used since the summing network loads the

output with approximately 275 Ω. Using this network in a

unity-gain configuration, settling time is 100 ns to 0.1% for a

–5 V to +5 V step with CL = 10 pF.

TO SCOPE

(TEK 7A11 FET PROBE)

R5

R6

D1

D2

R1

VIN

R2

R3

AD844

RL

VOUT

CL

D1, D2 IN6263 OR EQUIV. SCHOTTKY DIODE

Figure 9. Settling Time Test Fixture

DC Error Calculation

Figure 10 shows a model of the dc error and noise sources for

the AD844. The inverting input bias current, IBN, flows in the

feedback resistor. IBP, the noninverting input bias current, flows

in the resistance at Pin 3 (RP), and the resulting voltage (plus

any offset voltage) will appear at the inverting input. The total

error, VO, at the output is:

VO

= ( IBP

RP

+ VOS

+ IBN

RIN



)1

+

R1 

R2 

+

I BN

R1

Since IBN and IBP are unrelated both in sign and magnitude,

inserting a resistor in series with the noninverting input will not

necessarily reduce dc error and may actually increase it.

R1

Figure 8. Driving 1000 pF CL with Feed Forward Network

of Figure 7

Settling Time

Settling time is measured with the circuit of Figure 9. This

circuit employs a false summing node, clamped by the two

R2

VN

+~

INN

INP

RP

RIN

IBN

VOS

IBP

AD844

Figure 10. Offset Voltage and Noise Model for the AD844

–10–

REV. D

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